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lt1946 1 1946fb v in v in 3.3v sw fb lt1946 4.7 h d1 100nf 470pf 49.9k v out 8v 430ma 1946 f01 20 f 2.2 f v c gnd comp ss shdn off on c1: 2.2 f, x5r or x7r, 6.3v c2: 2 10 f, x5r or x7r, 10v d1: microsemi ups120 or equivalent l1: tdk rlf5018t-4r7m1r4 28.7k 5.23k tft-lcd bias supplies gps receivers dsl modems local power supplies 1.5a, 36v internal switch 1.2mhz switching frequency integrated soft-start function output voltage up to 34v low v cesat switch: 300mv at 1.5a (typ) 8v at 430ma from a 3.3v input small 8-lead msop package 1.2mhz boost dc/dc converter with 1.5a switch and soft-start figure 1. 3.3v to 8v, 430ma step-up dc/dc converter the lt 1946 is a fixed frequency step-up dc/dc converter containing an internal 1.5a, 36v switch. capable of gener- ating 8v at 430ma from a 3.3v input, the lt1946 is ideal for large tft-lcd panel power supplies. the lt1946 switches at 1.2mhz, allowing the use of tiny, low profile inductors and low value ceramic capacitors. loop com- pensation can be either internal or external, giving the user flexibility in setting loop compensation and allowing opti- mized transient response with low esr ceramic output capacitors. soft-start is controlled with an external capaci- tor, which determines the input current ramp rate during start-up. the 8-lead msop package and high switching frequency ensure a low profile overall solution less than 1.2mm high. load current (ma) 0 efficiency (%) 65 70 75 300 500 1946 f01b 60 55 50 100 200 400 80 85 90 efficiency features descriptio u applicatio s u typical applicatio u , lt, ltc and ltm are registered trademarks of linear technology corporation. all other trademarks are the property of their respective owners.
lt1946 2 1946fb package/order i for atio uu w t jmax = 125 c, ja = 40 c/w, jc = 10 c/w order part number ms8 part marking t jmax = 125 c, ja = 125 c/w (4-layer board) ltug lt1946ems8 1 2 3 4 v c fb shdn gnd 8 7 6 5 ss comp v in sw top view ms8 package 8-lead plastic msop order part number ms8 part marking ltbnw lt1946ems8e 1 2 3 4 8 7 6 5 top view ms8e package 8-lead plastic msop exposed pad (pin 9) is ground (must be soldered to pcb) v c fb shdn gnd ss comp v in sw 9 v in voltage ............................................................. 16v sw voltage ............................................... 0.4v to 36v fb voltage ............................................................. 2.5v shdn voltage ......................................................... 16v current into fb pin .............................................. 1ma (note 1) the denotes the specifications which apply over the full operating temperature range, otherwise specifications are at t a = 25 c. v in = 3v, v shdn = v in unless otherwise specified. (note 2) symbol conditions min typ max units minimum operating voltage 2.45 2.6 v maximum operating voltage 16 v feedback voltage 1.230 1.250 1.270 v 1.220 1.270 v fb pin bias current v fb = 1.250v (note 3) 20 120 na error amp transconductance ? i = 2 a40 mhos error amp voltage gain 300 v/v quiescent current v shdn = 2.5v, not switching 3.2 5 ma quiescent current in shutdown v shdn = 0v, v in = 3v 0 1 a reference line regulation 2.6v v in 16v 0.01 0.05 %/v switching frequency 0.9 1.2 1.4 mhz 0.8 1.5 mhz switching frequency in foldback v fb = 0v 0.4 mhz maximum duty cycle 86 90 % switch current limit (note 4) 1.5 2.1 3.1 a switch v cesat i sw = 1a 240 340 mv switch leakage current v sw = 5v 0.01 1 a soft-start charging current v ss = 0.5v 2.5 4 6 a absolute axi u rati gs w ww u electrical characteristics maximum junction temperature ......................... 125 c operating temperature range (note 2) .. 40 c to 85 c storage temperature range ................ 65 c to 150 c lead temperature (soldering, 10 sec)................. 300 c consult ltc marketing for parts specified with wider operating temperature ranges. order options tape and reel: add #tr lead free: add #pbf lead free tape and reel: add #trpbf lead free part marking: http://www.linear.com/leadfree/
lt1946 3 1946fb typical perfor a ce characteristics uw feedback pin voltage temperature ( c) ?0 feedback voltage (v) 1.27 25 1946 g01 1.24 1.22 ?5 0 50 1.21 1.20 1.28 1.26 1.25 1.23 75 100 125 feedback voltage (v) 0 1400 1200 1000 800 600 400 200 0 0.6 1.0 1946 g02 0.2 0.4 0.8 1.2 oscillator frequency (khz) t a = 30 ct a = 100 c t a = 25 c temperature ( c) ?0 0 current limit (a) 0.6 0.4 0.2 0.8 1.0 1.4 1.2 2.6 2.4 2.2 2.0 ?5 25 50 125 1946 g03 1.6 1.8 0 75 100 oscillator frequency current limit switch saturation voltage quiescent current switching waveforms for figure 1 circuit switch current (a) 0 v cesat (v) 0.20 0.25 0.30 1.2 1946 g04 0.15 0.10 0.4 0.8 0.2 1.4 0.6 1.0 1.6 0.05 0 0.35 temperature ( c) ?0 2.0 quiescent current (ma) 2.2 2.6 2.8 3.0 75 100 3.8 1946 g05 2.4 25 0 25 50 125 3.2 3.4 3.6 v out 20mv/div ac coupled v sw 5v/div 0v i li 0.5a/div ac coupled 0.5 s/div 1946 g06 the denotes the specifications which apply over the full operating temperature range, otherwise specifications are at t a = 25 c. v in = 3v, v shdn = v in unless otherwise specified. (note 2) symbol conditions min typ max units shdn input voltage high 2.4 v shdn input voltage low 0.5 v shdn pin bias current v shdn = 3v 16 32 a v shdn = 0v 0 0.1 a electrical characteristics note 1: stresses beyond those listed under absolute maximum ratings may cause permanent damage to the device. exposure to any absolute maximum rating condition for extended periods may affect device reliability and lifetime. note 2: the lt1946e is guaranteed to meet performance specifications from 0 c to 70 c. specifications over the 40 c to 85 c operating temperature range are assured by design, characterization and correlation with statistical process controls. note 3: current flows out of fb pin. note 4: current limit guaranteed by design and/or correlation to static test. current limit is independent of duty cycle and is guaranteed by design.
lt1946 4 1946fb + + a2 fb shdn shutdown v in 0.5v driver q1 0.01 ? 120k 90pf sw gnd comparator 5 v c 4 a 1 ss 8 comp 4 s rq ramp generator 1.2mhz oscillator 3 + + 2 3 1.250v reference 6 7 r1 (external) fb v out r2 (external) a3 a1 gnd (mse8 only) 9 1946 bd uu u pi fu ctio s v c (pin 1): error amplifier output pin. tie external com- pensation network to this pin, or use the internal compen- sation network by shorting the v c pin to the comp pin. fb (pin 2): feedback pin. reference voltage is 1.250v. connect resistive divider tap here. minimize trace area at fb. set v out according to v out = 1.250(1 + r1/r2). shdn (pin 3): shutdown pin. tie to 2.4v or more to enable device. ground to shut down. do not float this pin. gnd (pin 4): ground. tie directly to local ground plane. sw (pin 5): switch pin. this is the collector of the internal npn power switch. minimize the metal trace area con- nected to this pin to minimize emi. v in (pin 6): input supply pin. must be locally bypassed. comp (pin 7): internal compensation pin. provides an internal compensation network. tie directly to the v c pin for internal compensation. tie to gnd if not used. ss (pin 8): soft-start pin. place a soft-start capacitor here. upon start-up, 4 a of current charges the capacitor to 1.5v. use a larger capacitor for slower start-up. leave floating if not in use. exposed pad (ms8e, pin 9): ground. must be soldered to pcb. block diagra w figure 2. block diagram
lt1946 5 1946fb operatio u the lt1946 uses a constant frequency, current mode control scheme to provide excellent line and load regula- tion. please refer to figure 2 for the following description of the part? operation. at the start of the oscillator cycle, the sr latch is set, turning on the power switch q1. the switch current flows through the internal current sense resistor generating a voltage. this voltage is added to a stabilizing ramp and the resulting sum is fed into the positive terminal of the pwm comparator a2. when this voltage exceeds the level at the negative input of a2, the sr latch is reset, turning off the power switch. the level at the negative input of a2 (v c pin) is set by the error amplifier (a1) and is simply an amplified version of the difference between the feedback voltage and the reference voltage of 1.250v. in this manner, the error amplifier sets the correct peak current level to keep the output in regulation. two functions are provided to enable a very clean start-up for the lt1946. frequency foldback is used to reduce the oscillator frequency by a factor of 3 when the fb pin is below a nominal value of 0.5v. this is accomplished via comparator a3. this feature reduces the minimum duty cycle that the part can achieve thus allowing better control of the switch current during start-up. when the fb pin voltage exceeds 0.5v, the oscillator returns to the normal frequency of 1.2mhz. a soft-start function is also provided by the lt1946. when the part is brought out of shutdown, 4 a of current is sourced out of the ss pin. by connecting an external capacitor to the ss pin, the rate of voltage rise on the pin can be set. typical values for the soft-start capacitor range from 10nf to 200nf. the ss pin directly limits the rate of rise on the v c pin, which in turn limits the peak switch current. current limit is not shown in figure 2. the switch current is constantly monitored and not al- lowed to exceed the nominal value of 2.1a. if the switch current reaches 2.1a, the sr latch is reset regardless of the output of comparator a2. this current limit helps protect the power switch as well as the external compo- nents connected to the lt1946. applicatio s i for atio wu uu inductor selection several inductors that work well with the lt1946 are listed in table 1. this table is not exclusive; there are many other manufacturers and inductors that can be used. consult each manufacturer for more detailed information and for their entire selection of related parts, as many different sizes and shapes are available. ferrite core inductors should be used to obtain the best efficiency, as core losses at 1.2mhz are much lower for ferrite cores than for the cheaper powdered-iron ones. choose an inductor that can handle at least 1.5a without saturating, and ensure that the inductor has a low dcr (copper wire resistance) to mini- mize i 2 r power losses. a 4.7 h to 10 h inductor will be the best choice for most lt1946 designs. note that in some applications, the current handling requirements of the inductor can be lower, such as in the sepic topology where each inductor only carries one-half of the total switch current. the inductors shown in table 1 were chosen for small size. for better efficiency, use similar valued inductors with a larger volume. table 1. recommended inductors max size l dcr l w h part ( h) (m ? ) (mm) vendor cdrh5d18-4r1 4.1 57 5.7 5.7 2 sumida cdrh5d18-5r4 5.4 76 (847) 956-0666 cdrh5d28-5r3 5.3 38 5.7 5.7 3 www.sumida.com cdrh5d28-6r2 6.2 45 cdrh5d28-8r2 8.2 53 ell6sh-4r7m 4.7 50 6.4 6 3 panasonic ell6sh-5r6m 5.6 59 (408) 945-5660 ell6sh-6r8m 6.8 62 www.panasonic.com rlf5018t- 4.7 45 5.6 5.2 1.8 tdk 4r7m1r4 (847) 803-6100 www.tdk.com
lt1946 6 1946fb applicatio s i for atio wu uu capacitor selection low esr (equivalent series resistance) capacitors should be used at the output to minimize the output ripple voltage. multilayer ceramic capacitors are an excellent choice, as they have an extremely low esr and are available in very small packages. x5r or x7r dielectrics are preferred, as these materials retain the capacitance over wide voltage and temperature ranges. a 4.7 f to 20 f output capacitor is sufficient for most applications, but systems with very low output currents may need only a 1 f or 2.2 f output capacitor. solid tantalum or os-con capacitors can be used, but they will occupy more board area than a ceramic and will have a higher esr. always use a capacitor with a sufficient voltage rating. ceramic capacitors also make a good choice for the input decoupling capacitor, which should be placed as close as possible to the lt1946. a 2.2 f to 4.7 f input capacitor is sufficient for most applications. table 2 shows a list of several ceramic capacitor manufacturers. consult the manufacturers for detailed information on their entire selection of ceramic parts. table 2. ceramic capacitor manufacturers taiyo yuden (408) 573-4150 www.t-yuden.com avx (803) 448-9411 www.avxcorp.com murata (714) 852-2001 www.murata.com compensation?djustment to compensate the feedback loop of the lt1946, a series resistor-capacitor network should be connected from the comp pin to gnd. for most applications, a capacitor in the range of 220pf to 680pf will suffice. a good starting value for the compensation capacitor, c c , is 470pf. the compensation resistor, r c , is usually in the range of 20k to 100k. a good technique to compensate a new applica- tion is to use a 100k ? potentiometer in place of r c , and use a 470pf capacitor for c c . by adjusting the potentiom- eter while observing the transient response, the optimum value for r c can be found. figures 3a to 3c illustrate this process for the circuit of figure 1 with a load current stepped from 250ma to 300ma. figure 3a shows the tran- sient response with r c equal to 7.5k. the phase margin is v out 20mv/div ac coupled i li 0.5a/div ac coupled r c = 7.5k 200 s/div 1946 f03a figure 3a. transient response shows excessive ringing v out 20mv/div ac coupled i li 0.5a/div ac coupled r c = 18k 200 s/div 1946 f03b figure 3b. transient response is better v out 20mv/div ac coupled i li 0.5a/div ac coupled r c = 49.9k 200 s/div 1946 f03b figure 3c. transient response is well damped poor as evidenced by the excessive ringing in the output voltage and inductor current. in figure 3b, the value of r c is increased to 18k, which results in a more damped re- sponse. figure 3c shows the results when r c is increased further to 49.9k. the transient response is nicely damped and the compensation procedure is complete. the comp pin provides access to an internal resistor (120k) and capacitor (90pf). for some applications, these values will suffice and no external r c and c c will be needed.
lt1946 7 1946fb applicatio s i for atio wu uu compensation?heory like all other current mode switching regulators, the lt1946 needs to be compensated for stable and efficient operation. two feedback loops are used in the lt1946: a fast current loop which does not require compensation, and a slower voltage loop which does. standard bode plot analysis can be used to understand and adjust the voltage feedback loop. as with any feedback loop, identifying the gain and phase contribution of the various elements in the loop is critical. figure 4 shows the key equivalent elements of a boost converter. because of the fast current control loop, the power stage of the ic, inductor and diode have been replaced by the equivalent transconductance amplifier g mp . g mp acts as a current source where the output current is proportional to the v c voltage. note that the maximum output current of g mp is finite due to the current limit in the ic. from figure 4, the dc gain, poles and zeroes can be calculated as follows: output pole: p1= 2 2 r error amp pole: p2 = 1 2 r error amp zero: z1= 1 2 r dc gain: a = 1.25 v esr zero: rhp zero: z3 = high frequency pole: p3 > l o c out = c c c v grg r z esr c vr vl f out c c in ma o mp l out in l out s 2 2 2 2 2 1 2 2 3 + + g ma r c r o r2 c c : compensation capacitor c out : output capacitor g ma : transconductance amplifier inside ic g mp : power stage transconductance amplifier r c : compensation resistor r l : output resistance defined as v out divided by i load(max) r o : output resistance of g ma r1, r2: feedback resistor divider network 1946 f04 r1 c out r l v out v c c c g mp 1.250v reference figure 4. boost converter equivalent model the current mode zero is a right half plane zero which can be an issue in feedback control design, but is manageable with proper external component selection. using the circuit of figure 1 as an example, the following table shows the parameters used to generate the bode plot shown in figure 5. table 3. bode plot parameters parameter value units comment r l 18.6 ? application specific c out 20 f application specific r o 10 m ? not adjustable c c 470 pf adjustable r c 49.9 k ? adjustable v out 8 v application specific v in 3.3 v application specific g ma 40 mho not adjustable g mp 5 mho not adjustable l 5.4 h application specific f s 1.2 mhz not adjustable from figure 5, the phase is 120 when the gain reaches 0db giving a phase margin of 60 . this is more than adequate. the crossover frequency is 25khz, which is about three times lower than the frequency of the right half plane zero z2. it is important that the crossover frequency be at least three times lower than the frequency of the rhp zero to achieve adequate phase margin.
lt1946 8 1946fb applicatio s i for atio wu uu diode selection a schottky diode is recommended for use with the lt1946. the microsemi ups120 is a very good choice. where the input to output voltage differential exceeds 20v, use the ups140 (a 40v diode). these diodes are rated to handle an average forward current of 1a. for applications where the average forward current of the diode is less than 0.5a, an on semiconductor mbr0520 diode can be used setting output voltage to set the output voltage, select the values of r1 and r2 (see figure 1) according to the following equation: rr v v out 12 125 1 = ? ? ? ? ? ? . a good range for r2 is from 5k to 30k. layout hints the high speed operation of the lt1946 demands careful attention to board layout. you will not get advertised performance with careless layout. figure 6 shows the recommended component placement for a boost converter. frequency (hz) 0 gain (db) 50 100 100 10k 25k 100k 1m 1946 f05a ?0 1k frequency (hz) phase (deg) ?00 0 100 10k 25k 100k 1m 1946 f05b ?00 ?80 1k 60 figure 5. bode plot of figure 1? circuit figure 6. recommended component placement for boost converter. note direct high current paths using wide pc traces. minimize trace area at pin 1 (v c ) and pin 2 (fb). use multiple vias to tie pin 4 copper to ground plane. use vias at one location only to avoid introducing switching currents into the ground plane 1 2 8 7 3 4 6 5 l1 c2 lt1946 v out v in gnd shutdown r1 r2 multiple vias ground plane 1946 f06 c1 c ss c c r c +
lt1946 9 1946fb typical applicatio s u low profile, triple output tft supply (10v, ?0v, 20v) v in v in 3.3v to 5v sw fb 3 8 7 14 2 65 lt1946 l1 5.4 h d1 r2 10.5k r1 75k r c 33.3k 1946 ta01 c2 20 f c5 0.1 f c3 1 f c4 2.2 f c1 4.7 f c c 470pf c ss 100nf d4 v off ?0v 10ma av dd 10v 450ma, v in = 5v 275ma, v in = 3.3v v on 20v 5ma d5 c6 0.1 f v c gnd shdn ss comp c1 to c6: x5r or x7r c1: 4.7 f, 6.3v c2: 2 10 f, 10v c3: 1 f, 25v c4: 2.2 f, 10v c5, c6: 0.1 f, 10v d1: microsemi ups120 or equivalent d2 to d5: zetex bat54s or equivalent l1: sumida cdrh5d18-5r4 + d2 d3 off on av dd load current (ma) 0 efficiency (%) 65 70 75 300 500 1946 ta01a 60 55 50 100 200 400 80 85 90 v in = 5v v in = 3.3v v on load = 5ma v off load = 10ma efficiency av dd 50mv/div ac coupled i li 0.5a/div v in = 5v 100 s/div 1946 ta01b transient response 150ma 100ma av dd load
lt1946 10 1946fb typical applicatio s u 12v output boost converter efficiency v out 100mv/div ac coupled i li 0.5a/div v in = 3.3v 100 s/div 1946 ta02b transient response 175ma 100ma i load v in v in 3.3v to 5v sw fb lt1946 l1 4.7 h d1 c ss 100nf c c 470pf r c 33.3k v out 12v 410ma, v in = 5v 275ma, v in = 3.3v 1946 ta02 c2 4.7 f c1 4.7 f v c gnd comp ss shdn 3 65 4 7 8 2 1 c1: 4.7 f, x5r or x7r, 6.3v c2: 4.7 f, x5r or x7r, 16v d1: microsemi ups120 or equivalent l1: tdk rlf5018t-4r7m1r4 r1 84.5k r2 9.76k off on load current (ma) 0 efficiency (%) 65 70 75 300 500 1946 ta02a 60 55 50 100 200 400 80 85 90 v in = 5v v in = 3.3v
lt1946 11 1946fb u package descriptio ms8 package 8-lead plastic msop (reference ltc dwg # 05-08-1660) information furnished by linear technology corporation is believed to be accurate and reliable. however, no responsibility is assumed for its use. linear technology corporation makes no represen- tation that the interconnection of its circuits as described herein will not infringe on existing patent rights. msop (ms8) 0204 0.53 0.152 (.021 .006) seating plane note: 1. dimensions in millimeter/(inch) 2. drawing not to scale 3. dimension does not include mold flash, protrusions or gate burrs. mold flash, protrusions or gate burrs shall not exceed 0.152mm (.006") per side 4. dimension does not include interlead flash or protrusions. interlead flash or protrusions shall not exceed 0.152mm (.006") per side 5. lead coplanarity (bottom of leads after forming) shall be 0.102mm (.004") max 0.18 (.007) 0.254 (.010) 1.10 (.043) max 0.22 ?0.38 (.009 ?.015) typ 0.127 0.076 (.005 .003) 0.86 (.034) ref 0.65 (.0256) bsc 0 ?6 typ detail ? detail ? gauge plane 12 3 4 4.90 0.152 (.193 .006) 8 7 6 5 3.00 0.102 (.118 .004) (note 3) 3.00 0.102 (.118 .004) (note 4) 0.52 (.0205) ref 5.23 (.206) min 3.20 ?3.45 (.126 ?.136) 0.889 0.127 (.035 .005) recommended solder pad layout 0.42 0.038 (.0165 .0015) typ 0.65 (.0256) bsc msop (ms8e) 0603 0.53 0.152 (.021 .006) seating plane note: 1. dimensions in millimeter/(inch) 2. drawing not to scale 3. dimension does not include mold flash, protrusions or gate burrs. mold flash, protrusions or gate burrs shall not exceed 0.152mm (.006") per side 4. dimension does not include interlead flash or protrusions. interlead flash or protrusions shall not exceed 0.152mm (.006") per side 5. lead coplanarity (bottom of leads after forming) shall be 0.102mm (.004") max 0.18 (.007) 0.254 (.010) 1.10 (.043) max 0.22 ?0.38 (.009 ?.015) typ 0.127 0.076 (.005 .003) 0.86 (.034) ref 0.65 (.0256) bsc 0 ?6 typ detail ? detail ? gauge plane 12 3 4 4.90 0.152 (.193 .006) 8 8 1 bottom view of exposed pad option 7 6 5 3.00 0.102 (.118 .004) (note 3) 3.00 0.102 (.118 .004) (note 4) 0.52 (.0205) ref 1.83 0.102 (.072 .004) 2.06 0.102 (.081 .004) 5.23 (.206) min 3.20 ?3.45 (.126 ?.136) 2.083 0.102 (.082 .004) 2.794 0.102 (.110 .004) 0.889 0.127 (.035 .005) recommended solder pad layout 0.42 0.038 (.0165 .0015) typ 0.65 (.0256) bsc ms8e package 8-lead plastic msop (reference ltc dwg # 05-08-1662)
lt1946 12 1946fb ? linear technology corporation 2001 lt 0207 rev b ? printed in usa linear technology corporation 1630 mccarthy blvd., milpitas, ca 95035-7417 (408) 432-1900 fax: (408) 434-0507 www.linear.com low profile, triple output tft supply (8v, 8v, 23v) efficiency v in v in 3.3v sw fb lt1946 l1 5.4 h d1 r3 5.23k r2 28.7k r c 49.9k 1946 ta03 c2 20 f c5 0.1 f c6 0.1 f c7 0.1 f c4 1 f c3 2.2 f c1 4.7 f c c 470pf c ss 100nf d7 d2 d3 v off ?v 10ma av dd 8v 375ma v on 23v 5ma d6 c8 0.1 f v c gnd shdn 3 8 7 14 2 5 6 ss comp + d4 d5 c1 to c8: x5r or x7r c1: 4.7 f, 6.3v c2: 2 10 f, 10v c3: 2.2 f, 10v c4: 1 f, 25v c5, c6, c8: 0.1 f, 10v c7: 0.1 f, 16v d1: microsemi ups120 or equivalent d2 to d5: zetex bat54s or equivalent l1: sumida cdrh5d18-5r4 off on av dd load current (ma) 0 70 75 85 300 1946 ta03a 65 60 100 200 400 55 50 80 efficiency (%) v on load = 5ma v off load = 10ma start-up waveforms av dd 2v/div v on 10v/div v off 5v/div i in 200ma/v 1ms/div 1946 ta04 typical applicatio u part number description comments lt1613 1.4mhz switching regulator in 5-lead thinsot tm 5v at 200ma from 3.3v input, thinsot package lt1615 micropower constant off-time dc/dc converter in 5-lead thinsot 20v at 12ma from 2.5v, thinsot package lt1930/lt1930a 1.2mhz/2.2mhz, 1a switching regulator in 5-lead thinsot 12v at 300ma from 5v input, thinsot package lt1944/lt1944-1 dual 350ma boost converter v in = 1.2v to 15v, v out to 34v, ms10 package lt1945 dual 250ma boost converter v in = 1.2v to 15v, v out to 34v, ms10 package lt1946a 2.7mhz, 1.5a boost dc/dc converter v in = 2.45v to 16v, v out to 34v, ms8e package lt1947 3mhz, dual switching regulator 8v at 200ma from 3.3v input, 10-lead msop package thinsot is a trademark of linear technology corporation. related parts

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